Radio Frequency (RF) Receiver with Dynamic Frequency Planning and Method Therefor

ABSTRACT

A radio frequency (RF) receiver comprises an analog receiver, a digital processor, and a clock synthesizer. The analog receiver has an input for receiving an RF input signal, and an output for providing a digital intermediate frequency (IF) signal. The digital processor has a first input for receiving the digital IF signal, a second input for receiving a clock signal, a signal output for providing an IF output signal, and a control output for providing a clock control signal. The clock synthesizer has an input for receiving the clock control signal, and an output for providing the clock signal. The digital processor controls a frequency of the clock signal dynamically in response to a channel selection input to reduce interference of sub-harmonics created by the digital processor on the analog receiver.

CROSS REFERENCE TO RELATED, COPENDING APPLICATION

Related subject matter is found in a copending patent application,attorney docket number 1052-0053, application number unknown, entitled“Radio Frequency (RF) Receiver with Frequency Planning and MethodTherefor,” invented by Sherry X. Wu, Mustafa H. Koroglu, AlessandroPiovaccari, and Ramin K. Poorfard and assigned to the assignee hereof.

FIELD OF THE DISCLOSURE

The present disclosure relates generally to a radio frequency (RF)receivers, and more particularly to RF receivers subject to magneticcoupling of signals between circuits.

BACKGROUND

Radio frequency (RF) receivers are used in a wide variety ofapplications such as television receivers, cellular telephones, pagers,global positioning system (GPS) receivers, cable modems, cordlessphones, satellite radio receivers, and the like. As used herein, a“radio frequency” signal means an electrical signal conveying usefulinformation and having a frequency from about 3 kilohertz (kHz) tohundreds of gigahertz (GHz), regardless of the medium through which suchsignal is conveyed. Thus an RF signal may be transmitted through air,free space, coaxial cable, fiber optic cable, etc. One common type of RFreceiver is the so-called superheterodyne receiver. A superheterodynereceiver mixes the desired data-carrying signal with the output oftunable oscillator to produce an output at a fixed intermediatefrequency (IF). The fixed IF signal can then be conveniently filteredand converted down to baseband for further processing. Thus asuperheterodyne receiver requires two mixing steps.

Modern integrated circuit technology has allowed many of the circuitsused in RF receivers to be combined on-chip and thus to substantiallyreduce the cost of the RF receiver. However this level of integrationcreates other problems. For example, signals from one part of the chipmay be electrically or magnetically coupled to circuits in another partof the chip. These unwanted signal couplings can distort the desiredsignal and create artifacts that can be perceived by the viewer orlistener. Traditionally, integrated circuit designers have used layoutstrategies to reduce coupling between circuits, such as physicalseparation, the addition of ground rings, a reduction in the length ofconductors, etc. However these techniques, while still useful, areunable to completely eliminate the deleterious effects of electricallyor magnetically coupled energy.

BRIEF DESCRIPTION OF THE DRAWINGS

The present disclosure may be better understood, and its numerousfeatures and advantages made apparent to those skilled in the art byreferencing the accompanying drawings, in which:

FIG. 1 illustrates in partial block diagram and partial schematic form aradio frequency (RF) receiver according to an embodiment of the presentinvention;

FIG. 2 illustrates in partial block diagram and partial schematic form aportion of the RF receiver of FIG. 1 showing details of the clocksynthesizer;

FIG. 3 illustrates in block diagram form a portion of the TV tuner chipof FIG. 1 showing the coupling of RF energy from an aggressor circuit toother circuits;

FIG. 4 illustrates a flow diagram of a frequency planning algorithm usedby the TV tuner chip of FIG. 1;

FIG. 5 illustrates a graph of a tuning range of the TV tuner chip ofFIG. 1;

FIG. 6 illustrates a graph of a spectrum of a North American analogbroadcast television (NTSC) channel;

FIG. 7 illustrates a graph of a set of “W” curves for a televisionchannel; and

FIG. 8 illustrates a graph of a piecewise linear approximation of theset of “W” curves of FIG. 7.

The use of the same reference symbols in different drawings indicatessimilar or identical items.

DETAILED DESCRIPTION

FIG. 1 illustrates in partial block diagram and partial schematic form aradio frequency (RF) receiver 100 according to an embodiment of thepresent invention. RF receiver 100 is a multi-standard televisionreceiver capable of receiving both terrestrial and cable televisionsignals. Receiver 100 includes generally a signal source such as anantenna 110, a television (TV) tuner chip 120, a crystal 140, a digitaltelevision (DTV) demodulator 150, a display device 160, and aloudspeaker 170. Antenna 110 is capable of receiving broadcasttelevision signals and providing an RF input signal labeled “RF INPUT”(through a transformer, not shown in FIG. 1) to TV tuner chip 120. TVtuner chip 120 receives and filters a selected channel in the RF INPUTsignal indicated by an input labeled “CHANNEL SELECTION”, and convertsit to an intermediate frequency (IF) digital output signal labeled “IFOUTPUT”. DTV demodulator 150 receives and demodulates the IF OUTPUTsignal and separates the selected channel's spectrum into video andaudio signals that it provides to display device 160 and loudspeaker170, respectively.

TV tuner chip 120 includes an analog receiver 122, a digital processor124, and a clock synthesizer 126. Analog receiver 122 has an inputcoupled to antenna 110 through a balanced-unbalanced (balun)transformer, not shown in FIG. 1, a control input for receiving a signallabeled “TUNING CONTROL SIGNAL”, a clock input, and an output forproviding a digital intermediate frequency (IF) signal labeled “IF”. TheIF signal includes both an in-phase (I) component and a quadrature (Q)component.

Digital processor 124 includes a digital signal processor (DSP) 130 anda microcontroller (MCU) 132. DSP 130 has a signal input for receivingthe IF signal, a clock input for receiving a clock signal labeled“f_(CLK)”, and an output for providing signal IF OUTPUT. MCU 132 has aninput for receiving the CHANNEL SELECTION input, a clock input forreceiving f_(CLK), a first output for providing the TUNING CONTROLSIGNAL, and a second output for providing a signal labeled “CLOCKCONTROL SIGNAL”.

Clock synthesizer 126 has two terminals connected to crystal 140, acontrol input for receiving the CLOCK CONTROL SIGNAL from MCU 132, afirst output connected to the clock input of analog receiver 122, and asecond output for providing signal f_(CLK).

Generally, TV tuner chip 120 operates to tune a selected televisionchannel and output the channel to digital demodulator 150. Analogreceiver 122 tunes the selected channel by mixing it with a localoscillator signal whose frequency is chosen to mix the selected channelto a desired IF. In TV tuner chip 120, the desired IF is a low IF of 4MHz, but in TV tuner chip 120 the IF may also be chosen as a zero IF.Analog receiver 122 further processes the analog IF signal and convertsit to digital form using analog-to-digital converters (ADCs), not shown,for further processing in the digital domain by DSP 130. In addition tosupporting DTV receivers as illustrated, TV tuner chip 120 also supportsanalog television (ATV) receivers and integrates an ATV demodulator, notshown in FIG. 1, for that purpose.

MCU 132 performs frequency planning under the control of firmware. Itconverts the CHANNEL SELECTION input into an appropriate CLOCK CONTROLSIGNAL to clock synthesizer 126. MCU 132 includes a memory, such as aread-only memory (ROM) or FLASH memory, for storage of the firmware thatcontrols the frequency planning algorithm, as well as a serialinput/output port for receiving the CHANNEL SELECTION input.

Because it integrates circuitry operating at different frequencies, TVtuner chip 120 is susceptible to the harmful effects of undesired signalcoupling, known as spurs. A spur is any unwanted tonal energy generatedby the device itself. A spur can harm the signal in the wanted channeleither by acting as a co-channel, or if it corrupts the VCO, it canreciprocally mix with large blockers and hence hurt the wanted channel.However TV tuner chip 120 performs frequency planning for f_(CLK) totake into account the effects of three main spur coupling mechanisms.First, it takes into account the direct coupling of f_(CLK) and itsharmonics to other circuits. Digital processor 124 operates insynchronization with f_(CLK). As is conventional, f_(CLK) is a squarewave signal that has significant energy at its nominal frequency as wellas certain harmonic frequencies. If these signals are coupled tocircuits that tune or process the RF INPUT signal, undesired energycould be coupled into the passband of analog processor 122, distortingthe signal.

Second, f_(CLK) can mix with a signal generated in clock synthesizer 126to create a spur. The spur is harmful when its frequency overlaps withthe frequency of the desired channel.

Another spur mechanism is the generation and coupling of sub-harmonics.A sub-harmonic is a signal with energy that is generated at a fractionof a given frequency such as f_(CLK) and at harmonics of this fraction.In TV tuner chip 120, digital processor 124 operates in synchronism withthe f_(CLK) signal. Certain events, such as the switching of internalbuses, occur at intervals equal to an integer number of f_(CLK) periods.These switching events create energy that appears at frequencies lowerthan f_(CLK). What makes this mechanism particularly insidious is thatit is difficult to identify the primary sub-harmonic by using computersimulation alone, but may require observation on the chip, itself afterthe design is complete. For example in designing TV tuner chip 120, theinventors estimated from computer simulation that digital processor 124would generate a primary sub-harmonic at f_(CLK)/8 (and othersub-harmonics at harmonics of f_(CLK)/8). However when observing themanufactured chip, they discovered the primary sub-harmonic to actuallyoccur at f_(CLK)/16.

By using frequency planning, TV tuner chip 120 is able to change itsfrequency to any suitable frequency in the range of clock synthesizer126. In order to support frequency planning, TV tuner chip 120 includesa clock synthesizer, clock synthesizer 126, that is capable of changingits operating frequency from a nominal operating frequency tofrequencies within an available frequency range in small, discretesteps. In this way MCU 132, under the control of firmware stored in itsinternal program memory, is able to change f_(CLK) to a frequency thatreduces undesired coupling.

The techniques by which MCU 132 performs frequency planning for f_(CLK)will now be described with reference to FIGS. 2-8. FIG. 2 illustrates inpartial block diagram and partial schematic form a portion 200 of TVtuner chip 120 of FIG. 1 showing details of clock synthesizer 126.Portion 200 includes crystal 140 and clock synthesizer 126, whichincludes generally a crystal oscillator circuit 210, a divider 220, aphase locked loop (PLL) 230, and a divider 240.

Crystal oscillator circuit 210 includes two terminals connected torespective terminals of crystal 140. Crystal oscillator circuit 210inverts the signal between the terminals of crystal 140 to createoscillation and to provide a clock output signal to analog receiver 122.In the illustrated embodiment, crystal 140 is a low-cost crystal havinga standard frequency of 24 megahertz (MHz). Note that analog receiver122 additionally multiplies the 24 MHz clock signal according to theTUNING CONTROL SIGNAL to form a local oscillator signal to mix theselected channel to the desired IF.

Divider 220 has an input connected to the output of crystal oscillatorcircuit 210, and an output. In the illustrated embodiment, divider 220divides the 24 MHz output signal by six to produce a 4 MHz signal.

PLL 230 converts the 4 MHz signal to a multiplied signal. PLL 230 is adigital PLL that includes a phase detector 232, a loop filter 234, avoltage controlled oscillator (VCO) 236, and a feedback divider 238.Phase detector 232 has a positive input connected to the output ofdivider 220, a negative input, and an output. Loop filter 234 has aninput connected to the output of phase detector 232, and an output. VCO236 has an input connected to the output of loop filter 234, and anoutput for providing a multiplied signal. Feedback divider 238 has aninput connected to the output of VCO 236, a control input for receivingthe CLOCK CONTROL SIGNAL, and an output connected to the negative inputof phase detector 232. Feedback divider 238 changes the divide ratio ofthe VCO output signal according to the CLOCK CONTROL SIGNAL and inconjunction with phase detector 232 allows VCO 235 to provide themultiplied signal in 4 MHz frequency steps.

In the illustrated embodiment, the output of PLL 230 is a signal with anominal frequency of 1.6 gigahertz (GHz) but which may be varied inincrements of 4 MHz. Divider 240 is a fixed divider that divides theinput thereof by eight. As illustrated, it divides the 1.6 GHz±k*4 MHzsignal to a 200 MHz±k*500 kHz clock signal, in which the nominalfrequency of f_(CLK), is 200 MHz. Note that if f_(CLK) is increased toomuch, then the circuitry of TV tuner chip 120 may not operate properly.If it is decreased too much, then DSP 130 and MCU 132 may not haveenough bandwidth to perform the necessary processing tasks. Given theseconsiderations, the firmware in MCU 132 allows the operating frequencyof f_(CLK) to range between 190 MHz and 207 MHz in 1 MHz increments. Inother embodiments, the range and granularity of f_(CLK) may each beeither increased or decreased.

Thus clock synthesizer 126 is able to alter its output frequency insuitably fine increments over a range to move f_(CLK) to a frequencythat reduces harmful coupling and spur generation. It also does so usinga low-cost standard 24 MHz crystal.

The sources of undesired signal coupling will now be described withreference to FIG. 3, which illustrates in block diagram form a portion300 of TV tuner chip 120 of FIG. 1 showing the coupling of RF energyfrom an aggressor circuit to other circuits. Portion 300 includes a lownoise amplifier 310, a tracking filter 320, a crystal oscillator 330, asynthesizer with VCO 340, a mixer 350, and an aggressor circuit 360.Crystal oscillator 330 corresponds to both crystal 140 and crystaloscillator circuit 210 as shown in FIG. 2. Low noise amplifier 310,tracking filter 320, and mixer 330 correspond to analog receiver 122 ofFIG. 1. Aggressor circuit 360 includes DSP 130, MCU 132, and/or the ADCsof analog processor 122.

Aggressor circuit 360 transfers energy through magnetic flux created byinternal inductances, such as bond wires to external terminals.Inductances in the magnetically coupled circuits convert the magneticflux into unwanted electrical signals. As shown in FIG. 3, aggressorcircuit 360 couples signal energy, by magnetic coupling, primarily tothree points in TV tuner chip 120. First, aggressor 360 couples energyto the input of low noise amplifier 310. When this signal has energywithin the passband of tracking filter 320, it is mixed with the desiredTV channel and forms part of IF output.

Second, aggressor circuit 360 couples energy into the LO signal ofsynthesizer with VCO 340. This interfering energy creates spurs whenmixed with signals in the VCO, which distorts the local oscillatorsignal and thus distorts IF OUTPUT.

Third, aggressor circuit 360 couples energy into crystal oscillator 330,which it mixes with internal frequencies to generate spurs.

FIG. 4 illustrates a flow diagram of a frequency planning algorithm 400used by TV tuner chip 120 of FIG. 1. Frequency planning algorithm startsat step 402. At step 404, algorithm 400 chooses a default aggressorfrequency as the current frequency. At step 406, the algorithmdetermines, for this current frequency, whether it and its harmonicsfall within a selected channel of LNA 310. It is especially important toavoid this frequency since this energy will be passed by tracking filter320. Therefore if any harmonic of the current frequency falls within theselected channel, the current frequency is changed to the next aggressorfrequency at step 408.

If no frequency or harmonic falls within the passband, i.e. thefrequency and all harmonics fall outside the passband, then thealgorithm checks, at step 410, whether a spur falls within a desiredrange of crystal oscillator 330. The desired range is a range thatdoesn't produce any significant harmful spurs. If the spur does not fallin the desired range, then the flow returns to step 408 for theselection of a new f_(CLK) frequency. If the spur does fall in thedesired range, then the flow continues to step 412.

Step 412 determines whether the spur falls within the desired range ofsynthesizer 340. If so, then at step 414 the algorithm selects thecurrent frequency as the operating frequency, and then frequencyplanning algorithm 400 ends at step 428.

If not, then algorithm 400 determines whether secondary criteria are metby checking, at step 420, whether the spur falls within a secondarydesired band of synthesizer 340. As used herein, the secondary desiredband is first a “taboo” channel (frequency band that is not allocated toany channel), or second, a channel in which a blocker channel is not thestrongest, such as channels excluding the current channel ±6 channels or±12 channels. If the spur falls within the secondary desired band, thenalgorithm 400 logs the frequency at step 422. If the frequency is thelast frequency then algorithm 400 chooses, at step 426, the firstfrequency from the log as the operating frequency, and then ends at step428. If not, then flow returns to step 408.

By performing the frequency planning associated with flow chart 400, TVtuner chip 120 is able to significantly reduce direct coupling andharmful spur generation. The frequency planning firmware in TV tunerchip 120 also has a mechanism to prevent the harmful effects ofsub-harmonics, as will now be described with reference to FIGS. 5-8.FIG. 5 illustrates a graph 500 of a tuning range of TV tuner chip 120 ofFIG. 1. In FIG. 5, the horizontal axis represents frequency in Hz.Generally, TV tuner chip 120 supports various worldwide televisionstandards having channels between about 44 MHz and about 1 gigahertz(GHz). The actual channel placement and width varies according to theparticular standard selected.

As described above, digital processor 124 produces a primarysub-harmonic at 200 MHz/16, or 12.5 MHz, when fox is set to its nominalfrequency of 200 MHz, and additional sub-harmonics at N·f_(CLK)/16. Whena relatively low frequency channel spans a frequency of 50 MHz, 62.5MHz, 75 MHz, or 87.5 MHz, the nominal value of f_(CLK) creates asub-harmonic in-band for N=4, 5, 6, and 7.

However TV tuner chip 120 allows f_(CLK) to vary within a range of 190MHz to 207 MHz around its nominal frequency. Thus FIG. 5 illustrates asub-harmonic 510 at 47.5 MHz (for f_(CLK)=190 MHz) and a sub-harmonic520 at 51.75 MHz (for f_(CLK)=207 MHz). Thus for channels having certaincenter frequencies and a width that is 6 MHz wide (or for some supportedstandards, 8 MHz wide), it is not possible within the supported range ofclock synthesizer 126 to select a value of f_(CLK) to avoid placing asub-harmonic in-band.

However there exists a critical frequency 550, which is about 100 MHzfor TV tuner chip 120, at which the separation of the sub-harmonics isgreat enough for all sub-harmonics to be out of band for at least oneavailable value of f_(CLK). Near the high end of the tuning range, TVtuner chip 120 generates a first sub-harmonic 630 for 190 MHz that isseparated from a second sub-harmonic 540 for f_(CLK)=207 MHz by asignificant amount.

Accordingly, when the CHANNEL SELECTION signal indicates a channel thatlies above critical frequency 650, TV tuner chip 120 attempts to selecta value of f_(CLK) to move all sub-harmonics out-of-band. When theCHANNEL SELECTION signal indicates a channel that lies below criticalfrequency 550, TV tuner chip 120 selects a value of f_(CLK) thatproduces a sub-harmonic that is in-band but at a frequency that istolerable.

FIG. 6 illustrates a graph of a spectrum 600 of a North American analogbroadcast television (NTSC) channel. The graph includes a horizontalaxis showing relative frequency in MHz of a single NTSC channel. Thusthe channel may be at baseband, an IF, or RF. In the NTSC system,channels are 6.0 MHz wide. Spectrum 600 includes a lower band edge 610and an upper band edge 620 that is 6.0 MHz higher in frequency. As isconventional, the origin is considered to be a frequency of the videocarrier 630 (also known as the picture carrier), which places lower bandedge 510 at −1.25 MHz. A double sideband region is ±0.75 MHz aroundpicture carrier 630. The range of the spectrum below video carrier 630is considered to be the vestigial sideband, and the range between −1.25MHz and −0.75 MHz is considered to be a transition region. A furthertransition region occurs between 0.75 MHz and 1.25 MHz. A color carrier640 occurs at 3.58 MHz relative to picture carrier 630. A sound carrier650 occurs at 4.5 MHz relative to picture carrier 630. As can be readilyseen, a characteristic of television channels such as NTSC channels isthat the information content is not uniform within spectrum 600, but iscentered around video carrier 630, color carrier 640, and sound carrier650.

Moreover the qualitative effect of interfering signals across an NTSCchannel is also non-uniform, a fact which has been understood for quitesome time. FIG. 7 illustrates a graph 700 of a set of “W” curves 710 fora television channel. Set of “W” curves 710 was measured in 1986 andpublished by Weiss, S. et al., “New Measurements and Predictions of UHFTelevision Receiver Local Oscillator Radiation Interference,” Sep. 28,2003, available from URL h-e.com/pdfs/rw_bts03.pdf. In FIG. 7, thehorizontal axis represents frequency in MHz, and the vertical axis thelevel of interfering sine wave which experts rank as just perceptible,labeled “D/U RATIO”, in decibels with respect to the carrier (dBc).Graph 700 shows NTSC channel 23, transmitted between 524 MHz and 530MHz. Set of W curves 710 includes a first W curve 720, a second W curve730, and a third W curve 740, which represent perception thresholds fora gray screen, a still picture of a boat, and a moving picturerespectively. While the shape of the curves differ slightly, they allhave a similar shape with local minimums around the picture and colorcarriers. The picture and color carriers are frequencies at whichinterfering signals become perceptible at comparatively weak levels.

Ideally f_(CLK) could be selected to place all sub-harmonics out of thedesired band. However this objective is not always possible as describedwith respect to FIG. 5 above. Moreover because the frequency planningperformed by TV tuner chip 120 also takes into account chick signalcoupling and spur generation and coupling, it may be necessary to setf_(CLK) to a frequency in which a sub-harmonic falls somewhere withinthe channel. TV tuner chip 120 dynamically alters f_(CLK) according tothe CHANNEL SELECTION input to move the sub-harmonic to a leastobjectionable frequency given other constraints in the system.

Moreover it is possible to predetermine desired f_(CLK) frequencies foreach channel and to store these frequencies for later retrieval based onthe selected channel. However adding enough storage space to save allthese values on-chip is costly for a low-cost multi-standard integratedcircuit. For example, there are 158 channels in NTSC alone, and TV tunerchip 120 supports other broadcast standards including PAL and SECAM aswell as several variants of NTSC.

TV tuner chip 120 solves this problem by dynamically selecting thisleast objectionable frequency by approximating the characteristics ofthe “W” curve and using its available processing power to dynamicallydetermine the least objectionable f_(CLK) frequency for a channel thathas been selected. FIG. 8 illustrates a graph 800 of a piecewise linearapproximation 810 of set of “W” curves 810 of FIG. 4. In FIG. 8, thehorizontal axis represents frequency in MHz and the vertical axisrepresents weighting in units. Piecewise linear approximation 810includes a first segment 812 below lower band edge 830; a second segment814 between lower band edge 830 and the picture carrier, labeled“f_(PC)”; a third segment 816 between f_(PC) and an intermediatefrequency; a fourth segment 818 between the intermediate frequency andthe color carrier, labeled “f_(C)”; a fifth segment 820 between f_(C)and an upper band edge 840; and a sixth segment 822 above upper bandedge 840. By defining piecewise linear approximation 810 and using it toweight the subjective effect of the interfering sub-harmonic on theuser, and choosing the f_(CLK) frequency having the sub-harmonic withthe greatest weight to be considered the least objectionable frequency,TV tuner chip 120 is able to conserve storage space that would have beenneeded for a lookup table, and keep its cost low.

In another embodiment, the W curve can be expanded to take into accountimage frequencies. Since sub-harmonic energy at image frequencies can bemixed into the passband and not cancelled, this undesirable energy canbe significant as well. Also other appropriate rules can be used fortransmission systems other than NTSC. For example for North Americandigital television (ATSC) systems, the weighting function ensures thatany spurious energy does not land on the pilot frequency, which is about10 dB more sensitive than other in-band frequencies.

Thus TV tuner chip 120 achieves high integration and low cost byperforming dynamic frequency planning TV tuner chip 120 selects afrequency f_(CLK) at which to operate integrated digital circuitry basedon three coupling mechanisms: direct clock signal coupling, spurgeneration and coupling, and sub-harmonic coupling. TV tuner chip 120dynamically selects a least objectionable frequency based on the channelselected by the user. In other embodiments, TV tuner chip 120 mayimplement frequency planning for other coupling mechanisms or for onlyone or more of the ones described herein in various combinations.

The above-disclosed subject matter is to be considered illustrative, andnot restrictive, and the appended claims are intended to cover all suchmodifications, enhancements, and other embodiments that fall within thetrue scope of the claims. Thus, to the maximum extent allowed by law,the scope of the present invention is to be determined by the broadestpermissible interpretation of the following claims and theirequivalents, and shall not be restricted or limited by the foregoingdetailed description.

1. A radio frequency (RF) receiver comprising: an analog receiver havingan input for receiving an RF input signal, and an output for providing adigital intermediate frequency (IF) signal; a digital processor having afirst input for receiving said digital IF signal, a second input forreceiving a clock signal, a signal output for providing an IF outputsignal, and a control output for providing a clock control signal; aclock synthesizer having an input for receiving said clock controlsignal, and an output for providing said clock signal; wherein saiddigital processor controls a frequency of said clock signal dynamicallyin response to a channel selection input to reduce interference ofsub-harmonics created by said digital processor on said analog receiver.2. The RF receiver of claim 1 wherein said RF input signal is atelevision signal and said digital processor controls said frequency ofsaid clock, signal dynamically using a piecewise-linear approximation ofa W curve.
 3. The RF receiver of claim 2 wherein said piecewise-linearapproximation is derived from experimental data.
 4. The RF receiver ofclaim 2 wherein said piecewise-linear approximation includes a firstportion corresponding to a desired channel and a second portioncorresponding to an image channel.
 5. The RF receiver of claim 1 whereinsaid digital processor comprises a microcontroller (MCU) having a memoryfor storing firmware, wherein said MCU operates tinder control of saidfirmware to select said frequency of said clock signal.
 6. The RFreceiver of claim 1 wherein said analog receiver, said digitalprocessor, and said clock synthesizer are combined on a singleintegrated circuit.
 7. The RF receiver of claim 1 wherein said digitalprocessor controls said frequency of said clock signal dynamically inresponse to sub-harmonics produced by said digital processor.
 8. Amethod of frequency planning for a radio frequency (RF) receiver,comprising: creating a piecewise-linear approximation for weightinginterference; calculating a weight for a harmonic for each of aplurality of frequencies of a clock signal using said piecewise-linearapproximation; selecting said clock signal to have a frequencycorresponding to a favorable weighting of said harmonic; and clocking adigital processor using said clock signal while receiving an RF signal.9. The method of claim 8 wherein said clocking said digital processorfurther comprises clocking a digital signal processor (DSP).
 10. Themethod of claim 9 further comprising clocking a microcontroller (MCU)combined with said DSP on a single integrated circuit using said clocksignal.
 11. The method of claim 8 wherein said clocking said digitalprocessor comprises clocking said digital processor using said clocksignal while receiving a television signal.
 12. The method of claim 8wherein said creating said piecewise-linear approximation for weightingspurs comprises creating said piecewise-linear curve approximation onexperimental data.
 13. The method of claim 12 wherein said creating saidpiecewise-linear approximation for weighting interference furthercomprises creating said piecewise-linear approximation based on a Wcurve.
 14. The method of claim 8 further comprising repeating saidcreating, said calculating, said selecting, and said clocking inresponse to a change in a channel selection input.
 15. The method ofclaim 14 further comprising performing said repeating using amicrocontroller (MCU) integrated with an analog receiver on a singleintegrated circuit.
 16. The method of claim 8 wherein said creating saidpiecewise-linear approximation comprises creating a piecewise-linearapproximation having a first portion corresponding to a desired channeland a second portion corresponding to an image channel.
 17. A method offrequency planning for a radio frequency (RF) receiver, comprising:receiving a channel selection input for identifying a selected channelof a plurality of channels of an RF input signal; determining whetherany sub-harmonic of a clock signal will overlap a frequency spectrum ofsaid selected channel for at least one frequency of a plurality ofavailable frequencies of said clock signal; if no sub-harmonic of saidclock signal will overlap said frequency spectrum of said selectedchannel for at least one available frequency, selecting said at leastone available frequency as an operating frequency; if a sub-harmonic ofsaid clock signal will overlap said frequency spectrum of said selectedchannel for all of said plurality of available frequencies of said clocksignal, determining a weighting of sub-harmonics of said clock signalfor all of said plurality of available frequencies; selecting as saidoperating frequency one of said plurality of available frequencies witha favorable weighting; and operating a digital processor using saidclock signal at said operating frequency while receiving said RF inputsignal.
 18. The method of claim 17 wherein said determining comprisesdetermining whether said selected channel is below a predeterminedcritical frequency.
 19. The method of claim 18 wherein said RF inputsignal is a television signal and said determining further comprisesdetermining whether said selected channel is below 100 megahertz (MHz).20. The method of claim 17 wherein said determining comprises: creatinga piecewise-linear approximation for weighting interference; calculatinga weight for an interfering sub-harmonic for each of said plurality ofavailable frequencies of said clock signal using said piecewise-linearapproximation; and selecting as said operating frequency a frequencycorresponding to said interfering sub-harmonic with said favorableweighting.
 21. The method of claim 17 wherein said determining comprisesevaluating sub-harmonics each having a frequency equal to an integernumber N times a corresponding clock frequency divided by
 16. 22. Themethod of claim 17 wherein said operating comprises operating saiddigital processor using said clock signal at said operating frequencywhile receiving said RF input signal using an analog receiver combinedwith said digital processor on a single integrated circuit.